Techniques for using an electro-optical phase locked loop in a LIDAR system

ABSTRACT

A frequency modulated continuous wave (FMCW) light detection and ranging (LIDAR) system that includes an optical source to transmit an optical beam and a drive circuit configured to drive a current through the optical source to transmit the optical beam at a frequency. The system also includes an operational amplifier comprising a plurality of inputs to produce an output voltage for receipt by the drive circuit as input to determine an amplitude of the current driven by the drive circuit through the light source. The system also includes electro optical circuitry coupled to a first input of the plurality of inputs to produce a phase locked loop to maintain the light at the frequency. The system also includes ramp control circuitry coupled to a second input the plurality of inputs to cause the output voltage of the operational amplifier to modulate the optical beam at the frequency.

FIELD OF INVENTION

The present disclosure is related to light detection and ranging (LIDAR) systems.

BACKGROUND

In coherent LIDAR techniques such as Frequency-Modulated Continuous-Wave radar (FMCW) LIDAR, both the distance and the relative radial speed of a target affects the mixing frequency between the Local Oscillator (LO) and the return signal. To sense both distance and speed, conventional LIDAR systems typically use frequency modulation signals referred to as a down-chirp and an up-chirp. The down-chirp and the up-chirp can be carried within the same optical beam. Often a laser diode is used as an optical source for generating the optical beam. The laser diode generates light at a wavelength that is proportional to the magnitude of the current through it. Modulating the current in turn modulates the frequency of the light and generates the chirps. The current levels used to excite the laser diode may be several hundred milliamps or even as high as an Amp or more.

The cost of the circuitry used to generate and control the optical beams can be considerable. In particular, the power handling requirements of the circuitry dictate that many of the circuit components will be higher-power discrete elements coupled to a circuit board. Simplifying the circuitry and reducing the number of higher-power components can result in significant cost savings. This is particularly true if more of the circuit components can be incorporated into an integrated circuit as opposed to discrete elements.

BRIEF DESCRIPTION OF THE DRAWINGS

For a more complete understanding of the various examples, reference is now made to the following detailed description taken in connection with the accompanying drawings in which like identifiers correspond to like elements.

FIG. 1 is a block diagram of an example LIDAR system according to some embodiments of the present disclosure.

FIG. 2 is a time-frequency diagram of FMCW scanning signals that can be used by a LIDAR system according to some embodiments of the present disclosure.

FIG. 3 illustrates an example of a laser diode control circuit for a LIDAR system according to some embodiments of the present disclosure.

FIG. 4 illustrates another example of a laser diode control circuit for a LIDAR system according to some embodiments of the present disclosure.

FIG. 5 is a process flow diagram of an example method for operating a frequency modulated continuous wave (FMCW) light detection and ranging (LiDAR) system according to some embodiments of the present disclosure.

DETAILED DESCRIPTION

The present disclosure describes various examples of LIDAR systems and methods for detecting distance and relative speed of objects. More specifically, the present disclosure describes improved techniques for driving a laser diode.

Many LIDAR systems use a laser diode as an optical source for generating the optical beam used to scan the target environment. To measure distance and speed simultaneously or near simultaneously, the optical beam can be frequency modulated to generate up-chirps and down-chirps. Modulating the optical frequency involves modulating the flow of current through the laser diode.

The laser diode may be driven by a bias current that causes the laser diode to emit light at a base frequency and a modulation current that causes the frequency of the emitted light to vary around the base frequency. The current levels used to excite the laser diode may be any level of current great enough to stimulate laser emission. Typically, the bias current and the modulation current are driven by the same circuitry. The circuit components used to handle such large currents will usually be relatively large and often implemented in discrete circuit elements. In some LIDAR applications, the LIDAR equipment and associated circuitry may be expected to fit within a small form factor.

Embodiments of the present disclosure describe a laser diode control circuit that is simpler and can be implemented using smaller less expensive circuit components. The laser diode circuit in accordance with embodiments of the present disclosure includes an electro-optical phase locked loop (EOPLL), an operational amplifier (op-amp) to generate ramp signals, and a single-ended voltage-mode drive circuit that drives current through the laser diode in response to a voltage signal from the op-amp. The op-amp is configured as an integrator and has ramp control circuitry coupled to one of its inputs. The EOPLL is configured to maintain the light at the target frequency and is coupled to the other input of the op-amp. With this circuit, effective control of the laser diode can be achieved with fewer components that are able to fit within a smaller footprint. For example, the laser diode control circuit may be implemented with as few as two operational amplifiers (op-amps) and a minimal number of other simple components.

In some embodiments, the larger bias current can be delivered separately from the modulation current. For example, the drive circuit described above can be used to generate the modulation current, while a separate bias drive circuit generates the bias current. The bias current can be delivered through a separate path that does not include the EOPLL, the integrator, or the modulation drive circuit. Since the bias current is not in the EOPLL loop and does not affect the EOPLL or the modulation circuitry, the circuitry for driving the modulation current through the laser diode can be small enough to be suitable for implementation in the silicon of an integrated circuit. This enables most of the laser diode circuitry to be cheaper, more compact, and consume less power.

In the following description, reference may be made herein to quantitative measures, values, relationships or the like. Unless otherwise stated, any one or more if not all of these may be absolute or approximate to account for acceptable variations that may occur, such as those due to engineering tolerances or the like.

FIG. 1 is a block diagram of an example LIDAR system 100 according to example implementations of the present disclosure. The LIDAR system 100 includes one or more of each of a number of components but may include fewer or additional components than shown in FIG. 1 . As shown, the LIDAR system 100 includes optical circuits 101 implemented on a photonics chip. The optical circuits 101 may include a combination of active optical components and passive optical components. Active optical components may generate, amplify, and/or detect optical signals and the like. In some examples, the active optical component includes optical beams at different wavelengths, and includes one or more optical amplifiers, one or more optical detectors, or the like.

Free space optics 115 may include one or more optical waveguides to carry optical signals, and route and manipulate optical signals to appropriate input/output ports of the active optical circuit. The free space optics 115 may also include one or more optical components such as taps, wavelength division multiplexers (WDM), splitters/combiners, polarization beam splitters (PBS), collimators, couplers or the like. In some examples, the free space optics 115 may include components to transform the polarization state and direct received polarized light to optical detectors using a PBS, for example. The free space optics 115 may further include a diffractive element to deflect optical beams having different frequencies at different angles along an axis (e.g., a fast-axis).

In some examples, the LIDAR system 100 includes an optical scanner 102 that includes one or more scanning mirrors that are rotatable along an axis (e.g., a slow-axis) that is orthogonal or substantially orthogonal to the fast-axis of the diffractive element to steer optical signals to scan an environment according to a scanning pattern. For instance, the scanning mirrors may be rotatable by one or more galvanometers. Objects in the target environment may scatter an incident light into a return optical beam or a target return signal. The optical scanner 102 also collects the return optical beam or the target return signal, which may be returned to the passive optical circuit component of the optical circuits 101. For example, the return optical beam may be directed to an optical detector by a polarization beam splitter. In addition to the mirrors and galvanometers, the optical scanner 102 may include components such as a quarter-wave plate, lens, anti-reflective coated window or the like.

To control and support the optical circuits 101 and optical scanner 102, the LIDAR system 100 includes LIDAR control systems 110. The LIDAR control systems 110 may include a processing device for the LIDAR system 100. In some examples, the processing device may be one or more general-purpose processing devices such as a microprocessor, central processing unit, or the like. More particularly, the processing device may be complex instruction set computing (CISC) microprocessor, reduced instruction set computer (RISC) microprocessor, very long instruction word (VLIW) microprocessor, or processor implementing other instruction sets, or processors implementing a combination of instruction sets. The processing device may also be one or more special-purpose processing devices such as an application specific integrated circuit (ASIC), a field programmable gate array (FPGA), a digital signal processor (DSP), network processor, or the like.

In some examples, the LIDAR control systems 110 may include a signal processing unit 112 such as a DSP. The LIDAR control systems 110 are configured to output digital control signals to control optical drivers 103. In some examples, the digital control signals may be converted to analog signals through signal conversion unit 106. For example, the signal conversion unit 106 may include a digital-to-analog converter. The optical drivers 103 may then provide drive signals to active optical components of optical circuits 101 to drive optical sources such as lasers and amplifiers. In some examples, several optical drivers 103 and signal conversion units 106 may be provided to drive multiple optical sources.

The LIDAR control systems 110 are also configured to output digital control signals for the optical scanner 102. A motion control system 105 may control the galvanometers of the optical scanner 102 based on control signals received from the LIDAR control systems 110. For example, a digital-to-analog converter may convert coordinate routing information from the LIDAR control systems 110 to signals interpretable by the galvanometers in the optical scanner 102. In some examples, a motion control system 105 may also return information to the LIDAR control systems 110 about the position or operation of components of the optical scanner 102. For example, an analog-to-digital converter may in turn convert information about the galvanometers' position to a signal interpretable by the LIDAR control systems 110.

The LIDAR control systems 110 are further configured to analyze incoming digital signals. In this regard, the LIDAR system 100 includes optical receivers 104 to measure one or more beams received by optical circuits 101. For example, a reference beam receiver may measure the amplitude of a reference beam from the active optical component, and an analog-to-digital converter converts signals from the reference receiver to signals interpretable by the LIDAR control systems 110. Target receivers measure the optical signal that carries information about the range and velocity of a target in the form of a beat frequency, modulated optical signal. The reflected beam may be mixed with a second signal from a local oscillator. The optical receivers 104 may include a high-speed analog-to-digital converter to convert signals from the target receiver to signals interpretable by the LIDAR control systems 110. In some examples, the signals from the optical receivers 104 may be subject to signal conditioning by signal conditioning unit 107 prior to receipt by the LIDAR control systems 110. For example, the signals from the optical receivers 104 may be provided to an operational amplifier for amplification of the received signals and the amplified signals may be provided to the LIDAR control systems 110.

In some applications, the LIDAR system 100 may additionally include one or more imaging devices 108 configured to capture images of the environment, a global positioning system 109 configured to provide a geographic location of the system, or other sensor inputs. The LIDAR system 100 may also include an image processing system 114. The image processing system 114 can be configured to receive the images and geographic location and send the images and location or information related thereto to the LIDAR control systems 110 or other systems connected to the LIDAR system 100.

In operation according to some examples, the LIDAR system 100 is configured to use nondegenerate optical sources to simultaneously measure range and velocity across two dimensions. This capability allows for real-time, long-range measurements of range, velocity, azimuth, and elevation of the surrounding environment.

In some examples, the scanning process begins with the optical drivers 103 and LIDAR control systems 110. The LIDAR control systems 110 instruct the optical drivers 103 to independently modulate one or more optical beams, and these modulated signals propagate through the passive optical circuit to the collimator. The collimator directs the light at the optical scanning system that scans the environment over a preprogrammed pattern defined by the motion control system 105. The optical circuits 101 may also include a polarization wave plate (PWP) to transform the polarization of the light as it leaves the optical circuits 101. In some examples, the polarization wave plate may be a quarter-wave plate or a half-wave plate. A portion of the polarized light may also be reflected back to the optical circuits 101. For example, lensing or collimating systems used in LIDAR system 100 may have natural reflective properties or a reflective coating to reflect a portion of the light back to the optical circuits 101.

Optical signals reflected back from the environment pass through the optical circuits 101 to the receivers. Because the polarization of the light has been transformed, it may be reflected by a polarization beam splitter along with the portion of polarized light that was reflected back to the optical circuits 101. Accordingly, rather than returning to the same fiber or waveguide as an optical source, the reflected light is reflected to separate optical receivers. These signals interfere with one another and generate a combined signal. Each beam signal that returns from the target produces a time-shifted waveform. The temporal phase difference between the two waveforms generates a beat frequency measured on the optical receivers (photodetectors). The combined signal can then be reflected to the optical receivers 104.

The analog signals from the optical receivers 104 are converted to digital signals using ADCs. The digital signals are then sent to the LIDAR control systems 110. A signal processing unit 112 may then receive the digital signals and interpret them. In some embodiments, the signal processing unit 112 also receives position data from the motion control system 105 and galvanometers (not shown) as well as image data from the image processing system 114. The signal processing unit 112 can then generate a 3D point cloud with information about range and velocity of points in the environment as the optical scanner 102 scans additional points. The signal processing unit 112 can also overlay a 3D point cloud data with the image data to determine velocity and distance of objects in the surrounding area. The system also processes the satellite-based navigation location data to provide a precise global location.

FIG. 2 is a time-frequency diagram of FMCW scanning signals that can be used by a LIDAR system according to some embodiments. The FMCW scanning signals 200 and 202 may be used in any suitable LIDAR system, including the system 100, to scan a target environment. The scanning signal 200 may be a triangular waveform with an up-chirp and a down-chirp having a same bandwidth Δf_(s) and period T_(s). The other scanning signal 202 is also a triangular waveform that includes an up-chirp and a down-chirp with bandwidth Δf_(s) and period T_(s). However, the two signals are inverted versions of one another such that the up-chirp on scanning signal 200 occurs in unison with the down-chirp on scanning signal 202.

FIG. 2 also depicts example return signals 204 and 206. The return signals 204 and 206, are time-delayed versions of the scanning signals 200 and 202, where Δt is the round-trip time to and from a target illuminated by scanning signal 201. The round-trip time is given as Δt=2R/

, where R is the target range and v is the velocity of the optical beam, which is the speed of light c. The target range, R, can therefore be calculated as R=c(Δt/2).

In embodiments, the time delay Δt is not measured directly but is inferred based on the frequency differences between the outgoing scanning waveforms and the return signals. When the return signals 204 and 206 are optically mixed with the corresponding scanning signals, a signal referred to as a “beat frequency” is generated, which is caused by the combination of two waveforms of similar but slightly different frequencies. The beat frequency indicates the frequency difference between the outgoing scanning waveform and the return signal, which is linearly related to the time delay Δt by the slope of the triangular waveform.

If the return signal has been reflected from an object in motion, the frequency of the return signal will also be affected by the Doppler effect, which is shown in FIG. 2 as an upward shift of the return signals 204 and 206. Using an up-chirp and a down-chirp enables the generation of two beat frequencies, Δf_(up) and Δf_(dn). The beat frequencies Δf_(up) and Δf_(dn) are related to the frequency difference cause by the range, Δf_(Range), and the frequency difference cause by the Doppler shift, Δf_(Doppler), according to the following formulas: Δf _(up) =Δf _(Range) −Δf _(Doppler)  (1) Δf _(dn) =Δf _(Range) +Δf _(Doppler)  (2)

Thus, the beat frequencies Δf_(up) and Δf_(dn) can be used to differentiate between frequency shifts caused by the range and frequency shifts caused by motion of the measured object. Specifically, Δf_(Doppler) is the difference between the Δf_(up) and Δf_(dn) and the Δf_(Range) is the average of Δf_(up) and Δf_(dn).

The range to the target and velocity of the target can be computed using the following formulas:

$\begin{matrix} {{Range} = {\Delta f_{Range}\frac{cT_{s}}{2\Delta f_{s}}}} & (3) \end{matrix}$ $\begin{matrix} {{Velocity} = {\Delta f_{Doppler}\frac{\lambda_{c}}{2}}} & (4) \end{matrix}$ In the above formulas, λ_(c)=c/f_(c) and f_(c) is the center frequency of the scanning signal.

The beat frequencies can be generated, for example, as an analog signal in optical receivers 104 of system 100. The beat frequency can then be digitized by an analog-to-digital converter (ADC), for example, in a signal conditioning unit such as signal conditioning unit 107 in LIDAR system 100. The digitized beat frequency signal can then be digitally processed, for example, in a signal processing unit, such as signal processing unit 112 in system 100.

In some scenarios, to ensure that the beat frequencies accurately represent the range and velocity of the object, beat frequencies can be measured at the same moment in time, as shown in FIG. 2 . Otherwise, if the up-chirp beat frequency and the down-chirp beat frequencies were measured at different times, quick changes in the velocity of the object could cause inaccurate results because the Doppler effect would not be the same for both beat frequencies, meaning that equations (1) and (2) above would no longer be valid. In order to measure both beat frequencies at the same time, the up-chirp and down-chirp can be synchronized and transmitted simultaneously using two signals that are multiplexed together.

FIG. 3 illustrates an example of a laser diode control circuit implemented in a LIDAR system, according to some embodiments of the present disclosure. Components of the control circuit 300 may be included within the optical drivers 103 shown in FIG. 1 . As shown in FIG. 3 , the control circuit 300 includes an optical source 302 configured to emit one or more optical beams for performing LIDAR-based range and velocity detection, according to embodiments of the present invention. In some embodiments, the optical beam(s) may be a frequency-modulated continuous wave (FMCW) optical beam. It should be appreciated that optical beam output provided by the optical source 302 may be referred to herein as an outgoing, transmitted, or incident beam, while the beam reflected from the target may be referred to herein as the incoming, received, or return beam. The optical beam may be delivered to an optical scanner and emitted into a field of view (FOV) of the LIDAR system.

In some scenarios, a portion of the optical beam is captured by an optical receiver 304 and used to generate a feedback signal for an electro-optical phase locked loop (EOPLL) 306. The EOPLL 306 is configured to maintain the optical beam generated by the optical source 302 at the target frequency. As will be depicted in various embodiments herein, EOPLL 306 may be implemented in various scenarios in order to achieve the advantages disclosed herein.

As depicted in FIG. 3 , the control circuit 300 can include an op-amp 308 which includes the functionality to perform integrator circuit operations wherein the output signal is the time integral of its input signal. The op-amp 308 includes two inputs and a single output. For instance, one input may be configured as an inverting input that is coupled to ramp control circuitry 310 to control the modulation of a voltage signal output by the op-amp 308. A different input of op-amp 308 can be configured as a noninverting input that is coupled to the EOPLL 306 to control the output of the op-amp 308 to maintain the frequency of the optical beam at the target frequency. The voltage signal output by the op-amp 308 is used to control a current drive circuit 312, which drives a current through the optical source 302 responsive to the voltage signal.

In some embodiments, the current drive circuit 312 includes a drive circuit configured to generate a bias current and a separate drive circuit (not pictured) that is configured to generate a modulation current. In such embodiments, the bias current may be conducted through a separate path that does not include an EOPLL op-amp 308, and/or the control circuit 300 which controls only the modulation current. In other embodiments, the control circuit 300 may be configured to control both the bias current and the modulation current.

The control circuit 300 may be implemented in a single integrated circuit chip, as separate discrete circuit elements, or as a combination of discrete circuit elements and one or more integrated circuit chips. In some embodiments, the optical source 302 and some higher power components of the current drive circuit 312 are implemented as discrete circuit components mounted, for example, to a circuit board such as printed circuit board (PCB), while the lower power modulation circuitry, which includes the EOPLL 306, the op-amp 308, and the ramp circuitry 310, are implemented in an integrated circuit chip (e.g., silicon wafer). It will be appreciated that various alterations may be made to the system 300 and that some components may be omitted or added without departing from the scope of the disclosure. A more detailed description of an example laser diode control circuit is described further below.

FIG. 4 illustrates another example of a laser diode control circuit for a LIDAR system according to some embodiments of the present disclosure. Components of the control circuit 400 may be included within, for example, the optical drivers 103 shown in FIG. 1 .

The control circuit 400 of FIG. 4 includes a laser diode 402 that includes the functionality to generate an optical output. The frequency of the optical beam produced by the laser diode 402 is proportional to the amplitude of the current that drives the laser diode 402. Different values of input current can produce different values of optical beam frequency. Thus, the optical beam frequency changes with the ramping increases and/or decreases of the current when producing the laser light chirp. In this embodiment, the laser diode 402 is driven by a bias circuit 404 which is configured to drive a constant DC current through the laser diode 402, and a modulation circuit 406 that drives a linearly increasing or decreasing current through the laser diode 402 to produce the current modulation waveform.

The bias circuit 404 includes a bias transistor 426 that draws current through a bias path that includes the optical source 402 and a bias resistor 428 in a source follower configuration with the bias transistor 426. The bias transistor 426 is controlled by an operational amplifier (OpAmp) 408, which is configured as an error amplifier. The non-inverting input 430 of the operational amplifier 408 is coupled to a DC bias voltage 432, and the inverting input 434 is coupled to the source of the bias transistor 426 between the source and the bias resistor 428. The output of the operational amplifier 408 is coupled to the gate of the bias transistor 428. With this configuration, the operational amplifier 408 controls the bias transistor 426 so that the current through the bias transistor 426 causes the same DC voltage level to exist at the source of the bias transistor 426. Accordingly, the amplitude of the bias current will be determined by the amplitude of the DC bias voltage 432 (Vbias) and the resistance of the bias resistor 428 (Rbias).

It will be appreciated that various modifications can be made to the bias drive circuit 404 described above without deviating from the scope of the claims. For example, although the bias transistor 426 is shown as a field effect transistor (FET), the transistor may be any suitable variety, including a bipolar junction transistor (BJT), and others. Additionally, the bias resistor 428 may be positioned in a source follower configuration as shown or emitter follower configuration.

The modulation circuit 406 includes a modulation transistor 436 that draws current through the laser diode 402 and is controlled by an operational amplifier (OpAmp) 410, which is configured as an error amplifier. The amplitude of the modulation current drawn through the laser diode 402 will be determined by the amplitude of the voltage at the noninverting input of the modulation OpAmp 410 and the resistance of the modulation resistor 438. The control circuit 400 generates a modulated voltage signal that is input to the modulation circuit 406 so that the current through the laser diode 402 is modulated to generate the up chirps and down chirps.

It will be appreciated that various modifications can be made to the modulation drive circuit described above without deviating from the scope of the claims. For example, although the modulation transistor 436 is shown as a field effect transistor (FET), the transistor may be any suitable variety, including a bipolar junction transistor (BJT), and others. Additionally, the modulation resistor 438 may be positioned in a source follower configuration as shown or an emitter follower configuration.

To generate the modulated voltage signal, the control circuit 400 includes circuitry to produce an electro-optical phase locked loop (EOPLL) and can include an integrator circuit. The EOPLL 306 is a feedback loop that is configured to maintain the light generated by the optical source 402 at the target frequency. The circuitry used to produce the EOPLL 306 includes a phase frequency detector (PFD) 412, a charge Pump 414, a loop filter 416, and optical interferometer 418, and photodetector 420. Part of the light generated by the laser diode 402 is captured and input to the optical interferometer 418, which may be a Mach-Zehnder Interferometer (MZI), for example. The optical interferometer 418 splits the light into two different length paths, and then recombines the light into a single path. Any instantaneous difference in frequency of the two recombined light signals can be used to produce a beat frequency.

The beat frequency is detected by the photodetector 420, which in some embodiments, may be a photodiode followed by a transimpedance amplifier (PD/TIA) that converts the current signal from the photodiode into a voltage. The photodetector 420 detects the beat frequency from the combined light paths and feeds the beat frequency back to the PFD 412 as a voltage feedback signal, Vfb. The frequency of the voltage feedback signal will indicate the rate of change in the frequency of the light emitted by the laser diode 402.

The reference input, Vin 446, to the PFD 412 is an AC voltage signal whose frequency is used as a reference frequency that controls the rate of change (i.e., ramp rate) of the optical beam frequency. The PFD 412 detects the phase values of the reference and beat frequencies, and its output controls the switches of the charge pump 414 based on whether Vfb is lagging or leading Vin. If Vfb is lagging Vin, this indicates that the frequency of the optical signal output by the laser diode is too low and that the voltage driving the modulation transistor 410 is too low. Accordingly, to raise the voltage and thus the optical frequency, the “up” output of the PFD 412 is activated causing the loop filter 416 to be coupled to the positive current source and pulling the voltage, Vtune, up.

If Vfb is leading Vin this indicates that the frequency of the optical signal output by the laser diode 402 is too high and that the voltage driving the modulation transistor 410 is too high. Accordingly, to lower the voltage and thus the optical frequency, the “down” output of the PFD 412 is activated causing the loop filter 416 to be coupled to the negative current source and pulling the voltage, Vtune, down. In this way, the direction of the phase error values detected by the PFD 412 is used to control the charge pump 414 to raise or lower the voltage level of the non-inverting input of the OpAmp 422 through the loop filter 416.

The loop filter 416 operates according to a transfer function that integrates the current output from the charge pump 414 into a voltage and filters out at least some of the high frequency signal components. The loop filter 416 in this example is a circuit of one resistor and two capacitors. However, other arrangements are also possible depending on the desired transfer function. Additionally, the components of the loop filter 416 may be adjustable and controlled electronically to tune the electrical response of the loop filter 416.

The integrator includes the OpAmp 422, which is configured with a negative feedback current received through the capacitor, Cint. The integrator 422 performs the mathematical operation of integration with respect to time, which means that its output voltage is proportional to the input voltage integrated over time. Within certain operating conditions, this will result in the integrator outputting a ramp signal depending on the voltage at the inverting input. The integrator is controlled by ramp control circuitry 424, which is coupled to the inverting input of the operational amplifier 422 and configured to cause the output voltage of the operational amplifier 422 to ramp up or down in a linear or nearly linear fashion. Closing the Ramp_up switch connects the integrator to Vup and causes the voltage to increase. Closing the Ramp_dn switch connects the integrator to Vdn and causes the voltage to decrease. Closing the reset switch, RST, connects the input to Vtune, which causes the voltage to remain constant. Proper control of the ramp control switches can cause the integrator to generate a signal pattern, including a sawtooth pattern or the triangular pattern shown in FIG. 2 , for example. Any suitable voltages may be used depending on the desired waveform of the chirps. In some embodiments, Vtune may be set to approximately 1.5 Volts, Vup may be 1.0 Volts, and Vdn may be 2.0 Volts. Setting the voltages so that the magnitude of Vtune is halfway between Vup and Vdn in this way can generate equal magnitude up-chirps and down-chirps. However, other configurations are possible. Additionally, the timing of the switching can also be used to determine the shape of the chirp waveforms.

The OpAmp 410 of the modulation drive circuit 406 receives the single-ended control signal from the integrator at the non-inverting input and controls the gate of the modulation transistor 436 to cause a voltage between the transistor 436 and the modulation resistor 438 to equal a voltage level of the single-ended control signal received at the non-inverting input. In some embodiments, the integrator is coupled to the modulation drive circuit 406 through a coupling capacitor, Ccouple. The coupling capacitor may be configured to filter out high frequency components of the voltage signal generated by combined EEOPL and integrator. Additionally, the coupling capacitor, Ccouple, can be used to isolate the modulation drive circuit 406 during the reset stage, allowing the reset voltage signal applied to the modulation drive circuit 406 to be set to any desired value during the reset stage. In the embodiment shown in FIG. 4 , the input to the modulation drive circuit 406 is set to the voltage bias level, Vbias, during reset.

The particular values for the various circuit elements will vary depending on various design configurations for a particular implementation. In some embodiments, the bias current may be around 100 milliamps to several 100 milliamps, while the modulation current can range from less than 1 milliamp up more than half the bias current, but typically the bias current will be around 10 times greater than the modulation current. Thus, to handle the higher current, the bias transistor and bias resistor may be several times larger than the modulation transistor and the modulation resistor. In some embodiments, the bias transistor and bias resistor may be implemented as discrete components coupled to a circuit board, while the remainder of the circuit, including the modulation transistor 436 and modulation resistor 438 may be implemented in an integrated circuit chip.

FIG. 5 is a process flow diagram of an example method for operating a frequency modulated continuous wave (FMCW) light detection and ranging (LiDAR) system according to some embodiments of the present disclosure. The method 500 may be performed by any suitable LIDAR system and may be implemented by the laser diode control circuits 300 and 400 described above. The method may begin at block 502.

At block 502, a first voltage is delivered from an EOPLL to a first input of an op-amp. The op-amp may be configured as an integrator, and the first input may be non-inverting input. The EOPLL is configured to maintain the light output by the light source at the target frequency.

At block 504, a second voltage is delivered from a ramp control circuitry to a second input of the op-amp. The ramp control circuitry controls the modulation of the amplitude of the current through the light source.

At block 506, a drive circuit configured to drive a current through a light source is controlled by the output of the op-amp to generate light at the target frequency. The op-amp has a single output that delivers a voltage signal to the drive circuit and controls the drive circuit through single-ended signaling. In some embodiments, the voltage signal output by the op-amp controls both the modulation current and the bias current through the light source. In some embodiments, the drive circuit controls only the modulation current and the bias current is controlled by a separate bias drive circuit.

It will be appreciated that embodiments of the method 500 may include additional blocks not shown in FIG. 5 and that some of the blocks shown in FIG. 5 may be omitted. Additionally, the processes associated with blocks 502 through 508 may be performed in a different order than what is shown in FIG. 5 .

The preceding description sets forth numerous specific details such as examples of specific systems, components, methods, and so forth, in order to provide a thorough understanding of several examples in the present disclosure. It will be apparent to one skilled in the art, however, that at least some examples of the present disclosure may be practiced without these specific details. In other instances, well-known components or methods are not described in detail or are presented in simple block diagram form in order to avoid unnecessarily obscuring the present disclosure. Thus, the specific details set forth are merely exemplary. Particular examples may vary from these exemplary details and still be contemplated to be within the scope of the present disclosure.

Any reference throughout this specification to “one example” or “an example” means that a particular feature, structure, or characteristic described in connection with the examples are included in at least one example. Therefore, the appearances of the phrase “in one example” or “in an example” in various places throughout this specification are not necessarily all referring to the same example.

Although the operations of the methods herein are shown and described in a particular order, the order of the operations of each method may be altered so that certain operations may be performed in an inverse order or so that certain operation may be performed, at least in part, concurrently with other operations. Instructions or sub-operations of distinct operations may be performed in an intermittent or alternating manner.

The above description of illustrated implementations of the invention, including what is described in the Abstract, is not intended to be exhaustive or to limit the invention to the precise forms disclosed. While specific implementations of, and examples for, the invention are described herein for illustrative purposes, various equivalent modifications are possible within the scope of the invention, as those skilled in the relevant art will recognize. The words “example” or “exemplary” are used herein to mean serving as an example, instance, or illustration. Any aspect or design described herein as “example” or “exemplary” is not necessarily to be construed as preferred or advantageous over other aspects or designs. Rather, use of the words “example” or “exemplary” is intended to present concepts in a concrete fashion. As used in this application, the term “or” is intended to mean an inclusive “or” rather than an exclusive “or”. That is, unless specified otherwise, or clear from context, “X includes A or B” is intended to mean any of the natural inclusive permutations. That is, if X includes A; X includes B; or X includes both A and B, then “X includes A or B” is satisfied under any of the foregoing instances. In addition, the articles “a” and “an” as used in this application and the appended claims should generally be construed to mean “one or more” unless specified otherwise or clear from context to be directed to a singular form. Furthermore, the terms “first,” “second,” “third,” “fourth,” etc. as used herein are meant as labels to distinguish among different elements and may not necessarily have an ordinal meaning according to their numerical designation. 

What is claimed is:
 1. A frequency modulated continuous wave (FMCW) light detection and ranging (LIDAR) system, comprising: an optical source to transmit an optical beam; a drive circuit configured to drive a current through the optical source to transmit the optical beam at a frequency; an operational amplifier comprising a plurality of inputs to produce an output voltage for receipt by the drive circuit as input to determine an amplitude of the current driven by the drive circuit through the optical source; electro optical circuitry coupled to a first input of the plurality of inputs to produce a phase locked loop to maintain the optical beam at the frequency; and ramp control circuitry coupled to a second input the plurality of inputs to cause the output voltage of the operational amplifier to modulate the optical beam at the frequency; wherein the drive circuit comprises an error amplifier to control a transistor coupled in series with the optical source between a voltage source and ground.
 2. The FMCW LIDAR system of claim 1, wherein the drive circuit is a modulation drive circuit configured to drive a modulated current through the optical source, the LIDAR system further comprising a bias drive circuit configured to drive a constant bias current through the optical source.
 3. The FMCW LIDAR system of claim 2, wherein the bias drive circuit comprises a Field Effect Transistor (FET) driven by a DC voltage.
 4. The FMCW LIDAR system of claim 1, wherein the ramp control circuitry comprises a plurality of switches selectively coupleable to the second input of the operational amplifier to cause the output voltage of the operational amplifier to ramp linearly.
 5. The FMCW LIDAR system of claim 4, wherein: the electro optical circuitry coupled to the first input provides a first voltage level at the first input; and the plurality of switches comprises a ramp-up switch that couples a second voltage level to the second input and a ramp-down switch that couples a third voltage level to the second input, wherein the first voltage level is between the second voltage level and the third voltage level.
 6. The FMCW LIDAR system of claim 1, wherein an output of the operational amplifier is coupled to an input of the drive circuit through a coupling capacitor that enables the drive circuit to be isolated from the operational amplifier and coupled to a constant bias voltage through a reset switch during a reset stage.
 7. The FMCW LIDAR system of claim 1, wherein the optical beam is a frequency-modulated continuous wave (FMCW) optical beam.
 8. A method of operating a frequency modulated continuous wave (FMCW) light detection and ranging (LIDAR) system, comprising: delivering, via electro optical circuitry to produce a phase locked loop, a first voltage at a first input of an operational amplifier; delivering, via a ramp control circuitry, a second voltage at a second input of the operational amplifier, wherein an output of the operational amplifier ramps up or down based on a difference between the first voltage and the second voltage; controlling, via the output of the operational amplifier, a drive circuit configured to drive a current through a light source to generate an optical beam at a frequency; and controlling a bias drive circuit separately from the electro optical circuitry to drive a constant bias current through the light source.
 9. The method of claim 8, wherein the electro optical circuitry comprises a phase-frequency detector, the method comprising controlling a frequency of a reference clock input to the phase-frequency detector to control a rate of change of the output of the operational amplifier.
 10. The method of claim 8, wherein the electro optical circuitry comprises a charge pump and a loop filter, the method comprising varying a capacitance of one or more capacitors in the loop filter to vary a frequency response of the loop filter.
 11. The method of claim 8, wherein controlling the drive circuit comprises delivering a voltage at an output of the operational amplifier to an additional operational amplifier configured as an error amplifier that drives the current through the light source.
 12. The method of claim 8, comprising: emitting the optical beam towards a target and collecting light returned from the target in a return optical beam; generating a beat frequency from the return optical beam; and determining a range and velocity of the target from the beat frequency.
 13. A system for controlling a laser diode, comprising: a drive circuit comprising a transistor coupled in series with an optical source between a voltage source and ground and configured to deliver an amplitude modulated current through the optical source; an integrator coupled to the drive circuit to modulate the amplitude modulated current to generate an optical beam with a linearly varying frequency corresponding to an up-chirp and a down-chirp, wherein the integrator comprises an operational amplifier; and an electro optical circuitry to produce a phase locked loop, the electro optical circuitry to maintain the optical beam at the linearly varying frequency, wherein an output of the electro optical circuitry is coupled to a non-inverting input of the operational amplifier.
 14. The system of claim 13, wherein the drive circuit comprises an error amplifier.
 15. The system of claim 13, wherein the drive circuit is a modulation drive circuit configured to drive a modulated current through the optical source, the system further comprising a bias drive circuit configured to drive a constant bias current through the optical source.
 16. The system of claim 13, comprising a ramp control circuitry coupled to an inverting input of the operational amplifier and configured to control whether an amplitude of the amplitude modulated current ramps up or ramps down.
 17. The system of claim 16, wherein the electro optical circuitry provides a first voltage level at the non-inverting input, and wherein the ramp control circuitry comprises: a ramp-up switch that couples a second voltage level to the inverting input of the operational amplifier and a ramp-down switch that couples a third voltage level to the inverting input, wherein the first voltage level is halfway between the second voltage level and the third voltage level.
 18. The system of claim 13, wherein an output of the operational amplifier is coupled to an input of the drive circuit through a coupling capacitor, wherein a reset switch is coupled between the coupling capacitor and the input of the drive circuit, and wherein the reset switch is configured to apply a constant bias voltage to the input of the drive circuit during a reset stage. 